MC33368D DATASHEET PDF DOWNLOAD

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download the ON Semiconductor Soldering and Mounting Techniques. Reference Manual dimensions section on page 4 of this data sheet. ORDERING. MCD Datasheet (PDF) - ON Semiconductor. Part No. MCD. Download, MCD Click to view. File Size, Kbytes. Page, 20 Pages. JITONG TECHNOLOGY (CHINA HK & SZ) wfhm.info's Sponsor. Part: MC Maker: MOT. Pack: SOP. Stock: Reserved. Unit price for: $


Mc33368d Datasheet Pdf Download

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Single Stage Power Factor Controller, NCPDR2G datasheet, Electronic Components Datasheet Search Download, NCPDR2G Click to view Part Number, Components Description, Html View, Manufacturer. MC MCD Datasheet: High Voltage GreenLine Power Factor Controller, MCD PDF Download ON Semiconductor, MCD Datasheet PDF, Pinouts. Manufacturer: Motorola Solutions, Inc. Description: Power Factor Controller, Current-mode, A, CMOS, PDSO Download PDF. Print; Email; Bookmark.

Critical Conduction Mode boost converter with fixed output voltage. As shown in Figure 21, this approach creates a fixed V output voltage at the PFC output and a dc-dc converter is used to step the V down to 12 V output.

The controller used for the PFC front-end is the MC which offers some benefits over the other multiplier based critical conduction mode controllers. Critical Conduction Mode boost converter with variable output voltage. As shown in Figure 22, this approach creates uses a follower boost topology for the PFC section and creates a variable output V.

A dc-dc converter steps down the voltage to the 12 V output. Compared to approach 1, this approach is expected to yield better PFC stage efficiency and cost at the expense of a more challenging second stage design.

The MC is used as the PFC controller for this design also since it can be configured very easily in the follower boost mode. Continuous conduction mode boost converter with fixed output voltage.

As shown in Figure 23, this approach creates a fixed V output voltage using a CCM boost topology. Continuous conduction mode flyback converter with isolation and step down. This novel approach allows the consolidation of all circuitry into one single power conversion stage as shown in Figure The controller used for this approach is NCP Each converter went through minor modifications in order to achieve local optimization without making major component changes.

It is recognized that each approach can be optimized further through a more aggressive design and selection of components.

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However, the focus of this work was to compare the different approaches and the design approach for all the circuits was very similar. Each PFC circuit was tested for the following parameters: 1.

Line and load regulation 3. Input current total harmonic distortion THD , individual harmonic contributions, and power factor 4. Power conversion efficiency The test set-up is depicted in Figure 25 below.

The load current is measured using a 5. The voltage drop across the shunt resistor is measured and the load current can be calculated based on the shunt resistance value.

These are summarized in Chapter 5. As mentioned before, paper designs were performed for downconverter approaches D1-D3. It is noted that the designs D1 and D3 are identical as they have the same input and output specifications. The comparisons of complete system approaches are also provided in Chapter 5.

The key metrics for comparing power systems are cost, size and performance. Figure 1. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied.

MC Datasheet, HIGH VOLTAGE GREENLINEE POWER FACTOR CONTROLLER

Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. Quickstart Charge Current versus Temperature Figure 9.

Watchdog Timer Delay versus Temperature 6. Transient Thermal Resistance Figure With proper control of the preconverter, almost any complex load can be made to appear resistive to the ac line, thus significantly reducing the harmonic current content.

With the goal of exceeding the requirements of legislation on line current harmonic content, there is an ever increasing demand for an economical method of obtaining a unity power factor.

This data sheet describes a monolithic control IC that was specifically designed for power factor control with minimal external components. It offers the designer a simple cost effective solution to obtain the benefits of active power factor correction.

Most electronic ballasts and switching power supplies use a bridge rectifier and a bulk storage capacitor to derive raw dc voltage from the utility ac line, Figure Operating Description The MC contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. Referring to the block diagram in Figure 16, note that a multiplier has been added to the current sense loop and that this device does not contain an oscillator.

A description of each of the functional blocks is given below. The noninverting input is internally biased at 5.

The output voltage of the power factor converter is typically divided down and monitored by the inverting input. The Error Amplifier output is internally connected to the Multiplier and is pinned out Pin 4 for external loop compensation. The amplifier output stage can sink and source Note that by using a transconductance type amplifier, the input is allowed to move independently with respect to the output, since the compensation capacitor is connected to ground.

MC Datasheet (data sheet) PDF

Figure Uncorrected Power Factor Circuit This simple rectifying circuit draws power from the line when the instantaneous ac voltage exceeds the capacitor voltage. This occurs near the line voltage peak and results in a high charge current spike, Figure Since power is only taken near the line voltage peaks, the resulting spikes of current are extremely nonsinusoidal with a high content of harmonics. This results in a poor power factor condition where the apparent input power is much higher than the real power.

Power factor ratios of 0. This condition can occur during initial startup, sudden load removal, or during output arcing and is the result of the low bandwidth that must be used in the Error Amplifier control loop. The comparator threshold is internally set to 1. AC Line Current Figure The output voltage of the power factor converter is typically divided down and monitored by the inverting input.

The maximum input bias current is 1. A which can cause an output voltage error that is equal to the product of the input bias current and the value of the upper divider resistor 2. The Error Amplifier output is internally connected to the Multiplier and is pinned out Pin 4 for external loop compensation. Typically, the bandwidth is set below 2 Hz so that the amplifier s output voltage is relatively constant over a given ac line cycle.

In effect, the error amplifier monitors the average output voltage of the converter over several line cycles resulting in a fixed Drive Output ontime. The amplifier output stage can sink and source Note that by using a transconductance type amplifier, the input is allowed to move independently with respect to the output, since the compensation capacitor is connected to ground.

Overvoltage Comparator An Overvoltage Comparator is incorporated to eliminate the possibility of runaway output voltage. This condition can occur during initial startup, sudden load removal, or during output arcing and is the result of the low bandwidth that must be used in the Error Amplifier control loop. The Overvoltage Comparator monitors the peak output voltage of the converter, and when exceeded, immediately terminates MOFET switching.

The comparator threshold is internally set to 1. The ac haversines are monitored at Pin 5 with respect to ground while the Error Amplifier output at Pin 4 is monitored with respect to the oltage Feedback Input threshold.

A graph of the Multiplier transfer curve is shown in Figure 2. Note that both inputs are extremely linear over a wide dynamic range, to 3. The Multiplier output controls the Current ense Comparator threshold as the ac voltage traverses sinusoidally from zero to peak line.

This has the effect of forcing the MOFET ontime to track the input line voltage, thus making the preconverter load appear to be resistive. Pin 6 Threshold. The Zero Current Detector initiates the next ontime by setting the Latch at the instant the inductor current reaches zero. This critical conduction mode of operation has two significant benefits.

First, since the MOFET cannot turnon until the inductor current reaches zero, the output rectifier s reverse recovery time becomes less critical allowing the use of an inexpensive rectifier. To prevent false tripping, 2 m of hysteresis is provided. The Zero Current Detector input is internally protected by two clamps.

The upper clamp prevents input overvoltage breakdown while the lower. An external resistor must be used in series with the auxiliary winding to limit the current through the clamps to 5. Current ense Comparator and Latch The Current ense Comparator Latch configuration used ensures that only a single pulse appears at the Drive Output during a given cycle. The inductor current is converted to a voltage by inserting a groundreferenced sense resistor 7 in series with the source of output switch.

This voltage is monitored by the Current ense Input and compared to a level derived from the Multiplier output. The peak inductor current under normal operating conditions is controlled by the threshold voltage of Pin 6 where: Pin 6 Threshold I pk 7 Abnormal operating conditions occur when the preconverter is running at extremely low line or if output voltage sensing is lost. Under these conditions, the Current ense Comparator threshold will be internally clamped to 1.

Therefore, the maximum peak switch current is: I 1. The Current ense Input to Drive Output propagation delay is typically 2 ns. Timer A watchdog timer function was added to the IC to eliminate the need for an external oscillator when used in stand alone applications.

The Timer provides a means to automatically start or restart the preconverter if the Drive Output has been off for more than s after the inductor current reaches zero.

A Quickstart circuit has been incorporated to optimize converter startup. During initial startup, compensation capacitor C1 will be discharged, holding the Error Amplifier output below the Multiplier s threshold.

This will prevent Drive Output switching and delay bootstraping of capacitor C4 by diode D6. If Pin 4 does not reach the multiplier threshold before C4 discharges below the lower MP ULO threshold, the converter will hiccup and experience a significant startup delay.

The Quickstart circuit is designed to precharge C1 to 1.Power factor ratios of. A host of special purpose analog devices have also been developed. The Output Switching Frequency Clamp remedies this situation to improve power factor and minimize EMI generated in this operating region. This property allows for follower boost operation.

Each PFC circuit was tested for the following parameters: 1. Complete device specifications are provided in the form of Data Sheets which are categorized by product type into ten chapters for easy reference.

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